isl88731c Intersil Corporation, isl88731c Datasheet - Page 19

• Manufacturer Part Number: isl88731c
• Description: Smbus Level 2 Battery Charger
• Manufacturer: Intersil Corporation

Low switching loss requires low drain-to-gate charge
Q
higher the ON-resistance. Therefore, there is a trade-off
between the ON-resistance and drain-to-gate charge.
Good MOSFET selection is based on the Figure of Merit
(FOM), which is a product of the total gate charge and
on-resistance. Usually, the smaller the value of FOM, the
higher the efficiency for the same application.
For the low-side MOSFET, the worst-case power
dissipation occurs at minimum battery voltage and
maximum input voltage as shown in Equation 10.
Choose a low-side MOSFET that has the lowest possible
on-resistance with a moderate-sized package (like the
8 Ld SOIC) and is reasonably priced. The switching
losses are not an issue for the low-side MOSFET because
it operates at zero-voltage-switching.
Ensure that the required total gate drive current for the
selected MOSFETs should be less than 24mA. So, the
total gate charge for the high-side and low-side MOSFETs
is limited by Equation 11:
Where I
be less than 24mA. Substituting I
f
charge should be less than 80nC. Therefore, the
ISL88731C easily drives the battery charge current up
to 8A.
Snubber Design
ISL88731C's buck regulator operates in discontinuous
current mode (DCM) when the load current is less than
half the peak-to-peak current in the inductor. After the
low-side FET turns off, the phase voltage rings due to the
high impedance with both FETs off. This can be seen in
Figure 11. Adding a snubber (resistor in series with a
capacitor) from the phase node to ground can greatly
reduce the ringing. In some situations, a snubber can
improve output ripple and regulation.
The snubber capacitor should be approximately twice the
parasitic capacitance on the phase node. This can be
estimated by operating at very low load current (100mA)
and measuring the ringing frequency.
C
and 13:
P
Q
s
C
R
SNUB
gd
Q2
GATE
SNUB
SNUB
= 400kHz into Equation 11 yields that the total gate
. Generally, the lower the drain-to-gate charge, the
=
⎛
⎜
⎝
≤
and R
1
=
=
GATE
I
---------------- -
–
GATE
F
------------------------------------ -
(
SW
V
--------------- -
2πF
V
------------------- -
C
OUT
IN
2 L
SNUB
SNUB
is the total gate drive current and should
ring
⋅
2
⎞
⎟
⎠
⋅
)
I
2
BAT
can be calculated from Equations 12
⋅
L
2
⋅
r
DS ON
19
(
)
GATE
= 24mA and
(EQ. 12)
(EQ. 13)
(EQ. 10)
(EQ. 11)
ISL88731C
Input Capacitor Selection
The input capacitor absorbs the ripple current from the
synchronous buck converter, which is given by
Equation 14:
This RMS ripple current must be smaller than the rated
RMS current in the capacitor data sheet. Non-tantalum
chemistries (ceramic, aluminum, or OSCON) are
preferred due to their resistance to power-up surge
currents when the AC-adapter is plugged into the battery
charger. For Notebook battery charger applications, it is
recommended that ceramic capacitors or polymer
capacitors from Sanyo be used due to their small size
and reasonable cost.
Loop Compensation Design
ISL88731C has three closed loop control modes. One
controls the output voltage when the battery is fully
charged or absent. A second controls the current into the
battery when charging and the third limits current drawn
from the adapter. The charge current and input current
control loops are compensated by a single capacitor on
the ICOMP pin. The voltage control loop is compensated
by a network on the VCOMP pin. Descriptions of these
control loops and guidelines for selecting compensation
components will be given in the following sections. Which
loop controls the output is determined by the minimum
current buffer and the minimum voltage buffer shown in
the “FUNCTIONAL BLOCK DIAGRAM” on page 2. These
three loops will be described separately.
Transconductance Amplifiers GMV, GMI and
GMS
ISL88731C uses several transconductance amplifiers
(also known as gm amps). Most commercially available
op amps are voltage controlled voltage sources with gain
expressed as A = V
controlled current sources with gain expressed as
gm = I
for poles and zeros in the compensation.
PWM Gain F
The Pulse Width Modulator in the ISL88731C converts
voltage at VCOMP to a duty cycle by comparing VCOMP to
a triangle wave (duty = VCOMP/V
filter formed by L and C
output voltage (Vo = V
triangle wave amplitude is proportional to V
the ramp amplitude proportional to DCIN makes the gain
from VCOMP to the PHASE output a constant 11 and is
independent of DCIN. For small signal AC analysis, the
battery is modeled by its internal resistance. The total
output resistance is the sum of the sense resistor and the
internal resistance of the MOSFETs, inductor and capacitor.
Figure 22 shows the small signal model of the pulse width
modulator (PWM), power stage, output filter and battery.
I
rms
=
I
OUT
BAT
/V
V
IN
OUT
m
. gm will appear in some of the equations
(
V
V
OUT
IN
IN
−
DCIN
O
/V
V
OUT
convert the duty cycle to a DC
IN
*duty). In ISL88731C, the
. gm amps are voltage
)
P-P RAMP
). The low-pass
DCIN
September 9, 2010
. Making
(EQ. 14)
FN6978.1