ISL6527EVAL2 Intersil, ISL6527EVAL2 Datasheet - Page 11

• Manufacturer Part Number: ISL6527EVAL2
• Description: EVALUATION BOARD QFN ISL6527
• Manufacturer: Intersil

Specifications of ISL6527EVAL2

• Main Purpose: DC/DC, Step Down
• Outputs And Type: 1, Non-Isolated
• Voltage - Output: 0.75 ~ 3V
• Current - Output: 5A
• Voltage - Input: 3.3 ~ 5V
• Regulator Topology: Buck
• Frequency - Switching: 300kHz
• Board Type: Fully Populated
• Utilized Ic / Part: ISL6527
• Lead Free Status / RoHS Status: Contains lead / RoHS non-compliant
• Power - Output: -

error amplifier gain bounds the compensation gain. Check the
compensation gain at F
amplifier. The closed loop gain is constructed on the graph of
Figure 6 by adding the modulator gain (in dB) to the
compensation gain (in dB). This is equivalent to multiplying
the modulator transfer function to the compensation transfer
function and plotting the gain.
The compensation gain uses external impedance networks
Z
loop. A stable control loop has a gain crossing with
-20dB/decade slope and a phase margin greater than 45°.
Include worst-case component variations when determining
phase margin.
Component Selection Guidelines
Charge Pump Capacitor Selection
A capacitor across pins CT1 and CT2 is required to create the
proper bias voltage for the ISL6527, ISL6527A when operating
the IC from 3.3V. Selecting the proper capacitance value is
important so that the bias current draw and the current required
by the MOSFET gates do not overburden the capacitor. A
conservative approach is presented in Equation 11:
Output Capacitor Selection
An output capacitor is required to filter the output and supply
the load transient current. The filtering requirements are a
function of the switching frequency and the ripple current.
The load transient requirements are a function of the slew
rate (di/dt) and the magnitude of the transient load current.
These requirements are generally met with a mix of
capacitors and careful layout.
Modern digital ICs can produce high transient load slew
rates. High frequency capacitors initially supply the transient
and slow the current load rate seen by the bulk capacitors.
The bulk filter capacitor values are generally determined by
C
FIGURE 6. ASYMPTOTIC BODE PLOT OF CONVERTER GAIN
FB
100
PUMP
-20
-40
-60
80
60
40
20
0
and Z
10
MODULATOR
20
=
IN
log
I
------------------------------------
GAIN
BiasAndGate
to provide a stable, high bandwidth (BW) overall
⎛
⎝
V
100
R2
------- -
R1
CC
FZ1
⎞
⎠
×
f
s
FLC
1k
P2
×
FZ2
FREQUENCY (Hz)
1.5
with the capabilities of the error
FESR
10k
11
FP1
100k
FP2
1M
ERROR AMP GAIN
COMPENSATION
20
OPEN LOOP
LOOP GAIN
log
10M
GAIN
⎛
⎜
⎝
ISL6527, ISL6527A
----------------- -
V
(EQ. 11)
V
OSC
IN
⎞
⎟
⎠
the ESR (Effective Series Resistance) and voltage rating
requirements rather than actual capacitance requirements.
High frequency decoupling capacitors should be placed as
close to the power pins of the load as physically possible. Be
careful not to add inductance in the circuit board wiring that
could cancel the usefulness of these low inductance
components. Consult with the manufacturer of the load on
specific decoupling requirements.
Use only specialized low-ESR capacitors intended for
switching-regulator applications for the bulk capacitors. The
bulk capacitor’s ESR will determine the output ripple voltage
and the initial voltage drop after a high slew-rate transient. An
aluminum electrolytic capacitor’s ESR value is related to the
case size with lower ESR available in larger case sizes.
However, the Equivalent Series Inductance (ESL) of these
capacitors increases with case size and can reduce the
usefulness of the capacitor to high slew-rate transient loading.
Unfortunately, ESL is not a specified parameter. Work with
your capacitor supplier and measure the capacitor’s
impedance with frequency to select a suitable component. In
most cases, multiple electrolytic capacitors of small case size
perform better than a single large case capacitor.
Output Inductor Selection
The output inductor is selected to meet the output voltage
ripple requirements and minimize the converter’s response
time to the load transient. The inductor value determines the
converter’s ripple current and the ripple voltage is a function
of the ripple current. The ripple voltage and current are
approximated by Equations 12 and 13:
Increasing the value of inductance reduces the ripple current
and voltage. However, the large inductance values reduce
the converter’s response time to a load transient.
One of the parameters limiting the converter’s response to
a load transient is the time required to change the inductor
current. Given a sufficiently fast control loop design, the
ISL6527, ISL6527A will provide either 0% or 100% duty
cycle in response to a load transient. The response time is
the time required to slew the inductor current from an initial
current value to the transient current level. During this
interval the difference between the inductor current and the
transient current level must be supplied by the output
capacitor. Minimizing the response time can minimize the
output capacitance required.
The response time to a transient is different for the application
of load and the removal of load. Equations 14 and 15 give the
ΔI =
ΔV
OUT
V
IN
= ΔI x ESR
f
s
- V
x L
OUT
x
V
V
OUT
IN
November 18, 2008
(EQ. 12)
(EQ. 13)
FN9056.10