TOP258PN Power Integrations, TOP258PN Datasheet - Page 21

IC OFFLINE SWIT PROG OVP 8DIP

TOP258PN

Manufacturer Part Number
TOP258PN
Description
IC OFFLINE SWIT PROG OVP 8DIP
Manufacturer
Power Integrations
Series
TOPSwitch®-HXr
Type
Off Line Switcherr
Datasheet

Specifications of TOP258PN

Output Isolation
Isolated
Frequency Range
119 ~ 145kHz
Voltage - Output
700V
Power (watts)
77W
Operating Temperature
-40°C ~ 150°C
Package / Case
8-DIP (0.300", 7.62mm), 7 Leads
Output Voltage
700 V
Input / Supply Voltage (max)
9 V
Input / Supply Voltage (min)
- 0.3 V
Duty Cycle (max)
78 %
Switching Frequency
132 KHz
Operating Temperature Range
- 40 C to + 150 C
Mounting Style
SMD/SMT
Maximum Operating Temperature
+ 150 C
Minimum Operating Temperature
- 40 C
Output Current
6.88 A
Output Power
48 W
For Use With
596-1193 - KIT REF DESIGN TOP HX FOR TOP258
Lead Free Status / RoHS Status
Lead free / RoHS Compliant
Other names
596-1189-5

Available stocks

Company
Part Number
Manufacturer
Quantity
Price
Part Number:
TOP258PN
Manufacturer:
PowerInt
Quantity:
2 100
Part Number:
TOP258PN
Manufacturer:
PANASONIC
Quantity:
230
Application Examples
A High Effi ciency, 35 W, Dual Output - Universal Input
Power Supply
The circuit in Figure 41 takes advantage of several of the
TOPSwitch-HX features to reduce system cost and power
supply size and to improve effi ciency. This design delivers
35 W total continuous output power from a 90 VAC to 265 VAC
input at an ambient of 50 ºC in an open frame confi guration. A
nominal effi ciency of 84% at full load is achieved using
TOP258P. With a DIP-8 package, this design provides 35 W
continuous output power using only the copper area on the
circuit board underneath the part as a heat sink. The different
operating modes of the TOPSwitch-HX provide signifi cant
improvement in the no-load, standby, and light load
performance of the power supply as compared to the previous
generations of the TOPSwitch.
Resistors R3 and R4 provide line sensing, setting line UV at
100 VDC and line OV at 450 VDC.
Diode D5, together with resistors R6, R7, capacitor C6 and TVS
VR1, forms a clamp network that limits the drain voltage of the
TOPSwitch after the integrated MOSFET turns off. TVS VR1
provides a defi ned maximum clamp voltage and typically only
conducts during fault conditions such as overload. This allows
the RCD clamp (R6, R7, C6 and D5) to be sized for normal
operation, thereby maximizing effi ciency at light load. Should
the feedback circuit fail, the output of the power supply may
exceed regulation limits. This increased voltage at output will
also result in an increased voltage at the output of the bias
Figure 41. 35 W Dual Output Power Supply using TOP258PN.
www.powerint.com
90 - 265
L
E
N
VAC
3.15 A
F1
6.8 mH
L1
1 M
R1
275 VAC
220 nF
C3
1 M
10
RT1
R2
1N4937
1N4937
D1
D3
t
O
1N4007
1N4007
D2
D4
100 F
400 V
C4
2.0 M
2.0 M
22 k
R3
R4
2 W
R6
D
S
1/2 W
20
FR106
CONTROL
3.9 nF
R7
1 kV
D5
C6
M
100 nF
50 V
C8
P6KE200A
TOPSwitch-HX
5.1 k
C
VR1
R5
TOP258PN
U1
2
3
4
1N5250B
250 VAC
2.2 nF
EER28 7
VR2
20 V
C7
T1
6.8
11
R8
47 F
9
6
5
16 V
FR106
C9
D6
winding. Zener VR2 will break down and current will fl ow into
the “M” pin of the TOPSwitch initiating a hysteretic overvoltage
protection with automatic restart attempts. Resistor R5 will limit
the current into the M pin to < 336 μA, thus setting hysteretic
OVP. If latching OVP is desired, the value of R5 can be reduced
to 20 Ω.
The output voltage is controlled using the amplifi er TL431.
Diode D9, capacitor C20 and resistor R16 form the soft fi nish
circuit. At startup, capacitor C20 is discharged. As the output
voltage starts rising, current fl ows through the optocoupler diode
inside U2A, resistor R13 and diode D9 to charge capacitor C20.
This provides feedback to the circuit on the primary side. The
current in the optocoupler diode U2A gradually decreases as the
capacitor C20 becomes charged and the control amplifi er IC U3
becomes operational. This ensures that the output voltage
increases gradually and settles to the fi nal value without any
overshoot. Resistor R16 ensures that the capacitor C20 is
maintained charged at all times after startup, which effectively
isolates C20 from the feedback circuit after startup. Capacitor
C20 discharges through R16 when the supply shuts down.
Resistors R20, R21 and R18 form a voltage divider network.
The output of this divider network is primarily dependent on the
divider circuit formed using R20 and R21 and will vary to some
extent for changes in voltage at the 15 V output due to the
connection of resistor R18 to the output of the divider network.
Resistor R19 and Zener VR3 improve cross regulation in case
only the 5 V output is loaded, which results in the 15 V output
operating at the higher end of the specifi cation.
470 pF
100 V
4.7
C16
R10
PS2501-
1-H-A
U2B
33
R11
SB560
SB530
D7
D8
10 F
50 V
470 pF
C10
100 V
C12
10 F
10 k
50 V
C20
R16
33
R12
250 VAC
2.2 nF
C11
680 F
25 V
C13
1N4148
PS2501-
2200 F
1-H-A
330
U2A
D9
10 V
TL431
C17
R13
U3
2%
680 F
25 V
C14
10 k
R17
3.3 H
3.3 H
1 k
22
1.0 F
R15
L2
L3
R14
50 V
C19
TOP252-262
220 F
220 nF
25 V
C15
50 V
BZX55B8V2
C21
8.2 V
VR3
196 k
2%
220 F
R18
1%
10 V
C18
PI-4747-020508
10
R19
12.4 k
10 k
R21
1%
R20
1%
Rev. F 01/09
21
+12 V,
RTN
+5 V,
2.2 A
RTN
2 A

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