max5066auit Maxim Integrated Products, Inc., max5066auit Datasheet - Page 20

• Manufacturer Part Number: max5066auit
• Description: Max5066 Configurable, Single-/dual-output, Synchronous Buck Controller For High-current Applications
• Manufacturer: Maxim Integrated Products, Inc.

The output voltage is set by the combination of resistors
R1, R2, and R
section. First select a value for resistor R2. Then calculate
the value of R1 from the following equation:
where V
value of R
where ∆V
load to full load. R
is R5 and R7 in Figure 6.
The MAX5066 uses an average current-mode control
scheme to regulate the output voltage (see Figure 2).
The main control loop consists of an inner current loop
and an outer voltage loop. The voltage error amplifier
(VEA1 and VEA2) provides the controlling voltage for
the current loop in each phase. The output inductor is
“hidden” inside the inner current loop. This simplifies
the design of the outer voltage control loop and also
improves the power-supply dynamics. The objective of
the inner current loop is to control the average inductor
current. The gain-bandwidth characteristic of the cur-
rent loop can be tailored for optimum performance by
the compensation network at the output of the current-
error amplifier (CEA1 or CEA2). Compared with peak
current-mode control, the current-loop gain crossover
frequency, f
but the gain at low frequencies is much higher. This
results in the following advantages over peak current-
mode control.
1) The average current tracks the programmed cur-
2) Slope compensation is not required, but there is a
3) Noise immunity is excellent.
4) The average current-mode method can be used to
Configurable, Single-/Dual-Output, Synchronous
Buck Controller for High-Current Applications
20
rent with a high degree of accuracy.
limit to the loop gain at the switching frequency in
order to achieve stability.
sense and control the current in any circuit branch.
______________________________________________________________________________________
OUT(NL)
OUT
F
R
from the following equation:
1
C
F
, can be made approximately the same,
is the allowable drop in voltage from no
=
as described in the Voltage Error Amplifier
I
R
REVERSE
is the voltage at no load. Then find the
F
(
F
V
=
OUT NL
is R8 and R9, R1 is R4 and R6, R2
I
OUT
(
0 6135
=
.
Output-Voltage Setting
×
)
1 63
R
−
.
SENSE
0 6135
R
∆
.
V
SENSE
OUT
×
10
)
×
Compensation
−
36
×
3
R
×
2
R
1
For stability of the current loop, the amplified inductor-
current downslope at the negative input of the PWM
comparator (CPWM1 and CPWM2) must not exceed
the ramp slope at the comparator’s positive input. This
puts an upper limit on the current-error amplifier gain at
the switching frequency. The inductor current downs-
lope is given by V
inductor (L1 and L2 in Figure 6) and V
voltage. The amplified inductor current downslope at
the negative input of the PWM comparator is given by:
where R
in Figure 6) and g
amplifier (CEA_) at the switching frequency. The slope
of the ramp at the positive input of the PWM comparator
is 2V x f
maximum value of R
The highest crossover frequency f
or alternatively:
Equation (1) can now be rewritten as:
In practical applications, pick the crossover frequency
(f
First calculate R
such that:
where C
C
) in the range of:
SENSE
SW
CF
∆
∆
. Use the following equation to calculate the
is C10 and C12 in Figure 6.
V
R
R
t
L
C
CF
CF
f
CF
=
SW
is the current-sense resistor (R1 and R2
CF
≤
V
=
f
M
OUT
CMAX
=
=
L
V
V
OUT
in equation 2 above. Calculate C
2 π
OUT
IN
x R
CF
f
f
SW
10
CMAX
× ×
×
×
π
CF
(R14 or R15 in Figure 6).
/L where L is the value of the
=
R
R
×
×
<
S
SENSE
2π
10
2
R
f
f
is the gain of the current-error
f
f
C
C
SW
C
×
× ×
SENSE
×
V
<
2π
×
×
×
9
IN
f
SW
L
V
f
R
×
SW
OUT
×
2
CF
g
×
V
IN
V
×
M
36
CMAX
×
OUT
.
L
36
×
g
OUT
×
M
is given by:
g
2 ( )
×
M
is the output
R
CF
1 ( )
CF