EVAL-ADN2816EB Analog Devices Inc, EVAL-ADN2816EB Datasheet - Page 12

• Manufacturer Part Number: EVAL-ADN2816EB
• Manufacturer: Analog Devices Inc

Specifications of EVAL-ADN2816EB

• Lead Free Status / Rohs Status: Supplier Unconfirmed

ADN2816
THEORY OF OPERATION
The ADN2816 is a delay- and phase-locked loop circuit for
clock recovery and data retiming from an NRZ encoded data
stream. The phase of the input data signal is tracked by two
separate feedback loops that share a common control voltage. A
high speed delay-locked loop path uses a voltage controlled
phase shifter to track the high frequency components of input
jitter. A separate phase control loop, comprised of the VCO,
tracks the low frequency components of input jitter. The initial
frequency of the VCO is set by yet a third loop, which compares
the VCO frequency with the input data frequency and sets the
coarse tuning voltage. The jitter tracking phase-locked loop
(PLL) controls the VCO by the fine-tuning control.
The delay and phase loops together track the phase of the input
data signal. For example, when the clock lags input data, the
phase detector drives the VCO to a higher frequency and
increases the delay through the phase shifter; both of these
actions serve to reduce the phase error between the clock and
data. The faster clock picks up phase, while the delayed data
loses phase. Because the loop filter is an integrator, the static
phase error is driven to zero.
Another view of the circuit is that the phase shifter implements
the zero required for frequency compensation of a second-order
phase-locked loop, and this zero is placed in the feedback path
and, thus, does not appear in the closed-loop transfer function.
Jitter peaking in a conventional second-order phase-locked loop
is caused by the presence of this zero in the closed-loop transfer
function. Because this circuit has no zero in the closed-loop
transfer, jitter peaking is minimized.
The delay and phase loops together simultaneously provide
wideband jitter accommodation and narrow-band jitter
filtering. The linearized block diagram in Figure 13 shows that
the jitter transfer function, Z(s)/X(s), is a second-order low-pass
providing excellent filtering. Note that the jitter transfer has no
zero, unlike an ordinary second-order phase-locked loop. This
means that the main PLL has virtually zero jitter peaking (see
Figure 14). This makes this circuit ideal for signal regenerator
applications where jitter peaking in a cascade of regenerators
can contribute to hazardous jitter accumulation.
The error transfer, e(s)/X(s), has the same high-pass form as an
ordinary phase-locked loop. This transfer function is free to be
optimized to give excellent wideband jitter accommodation,
because the jitter transfer function, Z(s)/X(s), provides the
narrow-band jitter filtering.
Rev. A | Page 12 of 24
INPUT
d = PHASE DETECTOR GAIN
o = VCO GAIN
c = LOOP INTEGRATOR
psh = PHASE SHIFTER GAIN
n = DIVIDE RATIO
The delay and phase loops contribute to overall jitter accom-
modation. At low frequencies of input jitter on the data signal,
the integrator in the loop filter provides high gain to track large
jitter amplitudes with small phase error. In this case, the VCO is
frequency modulated and jitter is tracked as in an ordinary
phase-locked loop. The amount of low frequency jitter that can
be tracked is a function of the VCO tuning range. A wider
tuning range gives larger accommodation of low frequency
jitter. The internal loop control voltage remains small for small
phase errors; therefore, the phase shifter remains close to the
center of its range and thus contributes little to the low
frequency jitter accommodation.
DATA
X(s)
Figure 14. ADN2816 Jitter Response vs. Conventional PLL
RECOVERED
Figure 13. ADN2816 PLL/DLL Architecture
CLOCK
Z(s)
n psh
o
e(s)
FREQUENCY (kHz)
psh
JITTER TRANSFER FUNCTION
Z(s)
X(s)
TRACKING ERROR TRANSFER FUNCTION
X(s)
e(s)
d/sc
=
=
d psh
s
s
2
2
c
JITTER PEAKING
IN ORDINARY PLL
do
+
cn
s
d psh
1/n
+
s
c
s
2
1
n psh
o
+
o/s
do
cn
+ 1
ADN2816
X(s)
Z(s)