ISL6556ACBZ-T Intersil, ISL6556ACBZ-T Datasheet - Page 20

• Manufacturer Part Number: ISL6556ACBZ-T
• Description: IC CTRLR MULTIPHASE VRM10 28SOIC
• Manufacturer: Intersil

Specifications of ISL6556ACBZ-T

• Applications: Controller, Intel VR10X
• Voltage - Input: 3 ~ 12 V
• Number Of Outputs: 4
• Voltage - Output: 0.84 ~ 1.6 V
• Operating Temperature: 0°C ~ 70°C
• Mounting Type: Surface Mount
• Package / Case: 28-SOIC (7.5mm Width)
• Lead Free Status / RoHS Status: Lead free / RoHS Compliant

resistance of the bulk output-filter capacitance; and V
the peak-to-peak sawtooth signal amplitude as described in
Figure 4 and Electrical Specifications.
Once selected, the compensation values in Equations 21
assure a stable converter with reasonable transient
performance. In most cases, transient performance can be
improved by making adjustments to R
value of R
oscilloscope until no further improvement is noted. Normally,
C
Equations 21 unless some performance issue is noted.
The optional capacitor C
noise away from the PWM comparator (see Figure 12). Keep
a position available for C
frequency capacitor of between 22pF and 150pF in case any
leading-edge jitter problem is noted.
Output Filter Design
The output inductors and the output capacitor bank together
to form a low-pass filter responsible for smoothing the
pulsating voltage at the phase nodes. The output filter also
must provide the transient energy until the regulator can
respond. Because it has a low bandwidth compared to the
switching frequency, the output filter necessarily limits the
system transient response. The output capacitor must
supply or sink load current while the current in the output
inductors increases or decreases to meet the demand.
In high-speed converters, the output capacitor bank is
usually the most costly (and often the largest) part of the
circuit. Output filter design begins with minimizing the cost of
this part of the circuit. The critical load parameters in
choosing the output capacitors are the maximum size of the
load step, ΔI; the load-current slew rate, di/dt; and the
maximum allowable output-voltage deviation under transient
loading, ΔV
their capacitance, ESR, and ESL (equivalent series
inductance).
At the beginning of the load transient, the output capacitors
supply all of the transient current. The output voltage will
initially deviate by an amount approximated by the voltage
drop across the ESL. As the load current increases, the
voltage drop across the ESR increases linearly until the load
current reaches its final value. The capacitors selected must
have sufficiently low ESL and ESR so that the total output-
voltage deviation is less than the allowable maximum.
Neglecting the contribution of inductor current and regulator
response, the output voltage initially deviates by an amount
The filter capacitor must have sufficiently low ESL and ESR
so that ΔV < ΔV
Most capacitor solutions rely on a mixture of high-frequency
capacitors with relatively low capacitance in combination
ΔV
C
≈
will not need adjustment. Keep the value of C
(
ESL
C
)
di
---- -
dt
MAX
while observing the transient performance on an
+
(
MAX
. Capacitors are characterized according to
ESR
.
) ΔI
2
2
, is sometimes needed to bypass
, and be prepared to install a high-
20
C
. Slowly increase the
C
from
(EQ. 22)
PP
is
ISL6556A
with bulk capacitors having high capacitance but limited
high-frequency performance. Minimizing the ESL of the
high-frequency capacitors allows them to support the output
voltage as the current increases. Minimizing the ESR of the
bulk capacitors allows them to supply the increased current
with less output voltage deviation.
The ESR of the bulk capacitors also creates the majority of
the output-voltage ripple. As the bulk capacitors sink and
source the inductor ac ripple current (see Interleaving and
Equation 2), a voltage develops across the bulk-capacitor
ESR equal to I
are selected, the maximum allowable ripple voltage,
V
Since the capacitors are supplying a decreasing portion of
the load current while the regulator recovers from the
transient, the capacitor voltage becomes slightly depleted.
The output inductors must be capable of assuming the entire
load current before the output voltage decreases more than
ΔV
Equation 24 gives the upper limit on L for the cases when
the trailing edge of the current transient causes a greater
output-voltage deviation than the leading edge. Equation 25
addresses the leading edge. Normally, the trailing edge
dictates the selection of L because duty cycles are usually
less than 50%. Nevertheless, both inequalities should be
evaluated, and L should be selected based on the lower of
the two results. In each equation, L is the per-channel
inductance, C is the total output capacitance, and N is the
number of active channels.
Input Supply Voltage Selection
The VCC input of the ISL6556A can be connected either
directly to a +5V supply or through a current limiting resistor to
a +12V supply. An integrated 5.8V shunt regulator maintains
the voltage on the VCC pin when a +12V supply is used. A
300Ω resistor is suggested for limiting the current into the
VCC pin to a worst-case maximum of approximately 25mA.
Switching Frequency
There are a number of variables to consider when choosing
the switching frequency, as there are considerable effects on
the upper-MOSFET loss calculation. These effects are
outlined in MOSFETs, and they establish the upper limit for
the switching frequency. The lower limit is established by the
requirement for fast transient response and small output-
L
L
L
PP(MAX)
≤
≤
≥
MAX
2NCV
-------------------- - ΔV
(
------------------------- - ΔV
(
1.25
(
ESR
ΔI
(
ΔI
. This places an upper limit on inductance.
)
2
) NC
)
O
2
)
, determines the lower limit on the inductance.
(
--------------------------------------------------------- -
[
V
[
IN
f
S
C,PP
MAX
- N V
V
MAX
IN
V
- ΔI ESR
(ESR). Thus, once the output capacitors
OUT
PP MAX
- ΔI ESR
(
(
(
) V
OUT
)
)
]
)
] V
(
IN
- V
O
)
(EQ. 23)
(EQ. 24)
(EQ. 25)